UNISONIC TECHNOLOGIES CO., LTD TDA2030
14W HI-FI AUDIO AMPLIFIER
DESCRIPTION
The UTC TDA2030 is a monolithic audio power amplifier integrated circuit.

LINEAR INTEGRATED CIRCUIT

FEATURES
* Very low external component required. * High current output and high operating voltage. * Low harmonic and crossover distortion. * Built-in Over temperature protection. * Short circuit protection between all pins. * Safety Operating Area for output transistors.

*Pb-free plating product number: TDA2030L

ORDERING INFORMATION
Ordering Number Normal Lead Free Plating TDA2030-TA5-T TDA2030L-TA5-T TDA2030-TB5-T TDA2030L-TB5-T Package TO-220-5 TO-220B Packing Tube Tube

PIN CONFIGURATION
PIN NO. 1 2 3 4 5 PIN NAME Non inverting input Inverting input -VS Output +VS

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ABSOLUTE MAXIMUM RATINGS (Ta=25°C)

LINEAR INTEGRATED CIRCUIT

PARAMETER SYMBOL RATINGS UNIT 18 Supply Voltage Vs V Input Voltage VIN Vs V 15 Differential Input Voltage VI(DIFF) V Peak Output Current(internally limited) IOUT 3.5 A Total Power Dissipation at Tc=90°C PD 20 W Junction Temperature TJ -40~+150 °C Storage Temperature TSTG -40~+150 °C Note: Absolute maximum ratings are those values beyond which the device could be permanently damaged. Absolute maximum ratings are stress ratings only and functional device operation is not implied.

ELECTRICAL CHARACTERISTICS (Refer to the test circuit, Vs
PARAMETER Supply Voltage Quiescent Drain Current Input Bias Current Input Offset Voltage Input Offset Current Power Bandwidth SYMBOL TEST CONDITIONS Vs IQ II(BIAS) Vs 18v VI(OFF) II(OFF) BW POUT=12W, RL=4Ω, Gv=30dB d=0.5%, Gv=30dB RL=4Ω f=40Hz to 15KHz RL=8Ω POUT d=10%, Gv=30dB RL=4Ω f=1KHz RL=8Ω Gvo Gvc f=1kHz POUT=0.1 to 12W, RL=4Ω f=40Hz to 15KHz, Gv=30dB THD POUT=0.1 to 8W, RL=8Ω f=40Hz to 15KHz, Gv=30dB eN B= 22Hz to 22kHz iN B= 22Hz to 22kHz RIN RL=4Ω, Gv=30dB Rg=22kΩ, fripple=100Hz, SVR Vripple=0.5Veff TJ

16V,Ta=25°C) MIN 6 TYP 40 0.2 2 20 12 8 MAX 18 60 2 20 200 UNIT V mA µA MV NA Hz W W W W dB dB % % µV pA MΩ dB °C

Output Power

Open Loop Voltage Gain Closed Loop Voltage Gain Distortion

10~140,000 14 9 18 11 90 29.5 30 30 .5 0.2 0.1 3 80 5 50 145 0.5 0.5 10 200

Input Noise Voltage Input Noise Current Input Resistance(pin 1) Supply Voltage Rejection Thermal Shut-Down Junction Temperature

0.5 40

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TEST CIRCUIT

LINEAR INTEGRATED CIRCUIT

APPLICATION CIRCUIT
+ Vs C5 220 F 1 R3 22k 2 UTC TDA 2030 3 R1 13k R3 680 C2 22 F C6 100 F D1 1N4001 C4 C7 100nF 220nF C3 100nF D1 1N4001 5 4 R4 1 RL

Vi

C1 1 F

-Vs

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TYPICAL CHARACTERISTICS
Fig.2 Open loop frequency response
140

LINEAR INTEGRATED CIRCUIT

Fig.3 Output power vs. Supply voltage
Phase
180 24 Gv=26dB d=0.5% f=40 to 15kHz RL=4

Phase
100 90

20

PoUT (W)

Gv(dB)

60

0

16 RL=8 12

Gain
20

-20

8

-60

4 1 10 2 10 3 10 4 10 5 10 6 10 7 10 24 28 32 36 40 44

Frequency (Hz)

Vs (V)

Fig.4 Total harmonic distortion vs. output power
2 10 2 10

Fig.5 Two tone CCIF intermodulation distortion

1 10

Gv=26dB d( % )

1 10

d( % )

0 10

Vs=38V RL=8 f=15kHz Vs=32V RL=4 f=1kHz

0 10

Vs=32V PoUT=4W RL=4 Gv=26dB Order (2f1-f2) Order (2f2-f1)

-1 10

-1 10

-2 10 -2 10

-1 10

0 10

1 10

2 10

-2 10

1 10

2 10

3 10

4 10

5 10

Po (W)

Frequency (Hz)

Fig.6 Large signal frequency response
30 30

Fig.7 Maximum allowable power dissipation vs. ambient temperture

Vs=+-15V RL=8
25 25

Vo(Vp-p)

20

PD (W)

Vs=+-15V RL=4

20 ink ats he te ini inf ving ha ink C/W ° ats he h=25 Rt

15

15

10

10

he at Rt sink h= h 4° av C/ ing he ats W ink Rt ha h= vi 8° C/ ng W

5 1 10 2 10 3 10 4 10

5 -50 0 50 100 150 200

Frequency (kHz)

Ta (°C)

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+Vs
C3 0.22 F C5 220 F /40V

LINEAR INTEGRATED CIRCUIT

Vi

1
R3 56k C2 22 F R2 56k

1N4001

C1 2.2 F

R1 56k

R6 1.5

5
C6 0.22 F

UTC TDA2030 2 3
R5 30k R7 1.5

4
1N4001

C8 2200 F

R8 1 RL=4 C7 0.22 F

R4 3.3k C4 10 F

Fig. 1 Single supply high power amplifier

TYPICAL PERFORMANCE OF THE CIRCUIT OF FIG. 1
PARAMETER Supply Voltage Quiescent Drain Current SYMBOL Vs IQ TEST CONDITIONS Vs=36V d=0.5%,RL=4Ω f=40Hz to 15kHz,Vs=39V d=0.5%,RL=4Ω f=40Hz to 15kHz,Vs=36V d=10%,f=1kHz, RL=4Ω,Vs=39V d=10%,RL=4Ω f=1kHz,Vs=36V f=1kHz POUT=20W,f=1kHz POUT=20W,f=40Hz to 15kHz Gv=20dB,POUT=20W, f=1kHz,RL=4Ω RL=4Ω,Rg=10kΩ B=curve A,POUT=25W RL=4Ω,Rg=10kΩ B=curve A,POUT=4W MIN TYP 36 50 35 28 W 44 35 19.5 20 8 0.02 0.05 890 108 100 20.5 dB V/µsec % % mV dB MAX 44 UNIT V mA

Output Power

POUT

Voltage Gain Slew Rate Total Harmonic Distortion Input Sensitivity

Gv SR d VIN

Signal to Noise Ratio

S/N

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TYPICAL PERFORMANCE CHARACTERISTICS
Output Power vs. Supply Voltage

LINEAR INTEGRATED CIRCUIT

Total Harmonic Distortion vs. Output Power

45 10 0

Vs=36V RL=4 Gv=20dB

35

25 10 -1 f=15kHz 15 f=1kHz 5

24

28

32

34 Vs (V)

36

40

10 -2

10-1

100

PoUT (W)

101

Output Power vs. Input Level

Power Dissipation vs. Output Power

20 Gv=26dB 15 Gv=20dB 10

20

Complete Amplifier

15 10
UTC TDA2030

5 0 100 250 400 550 VIN (mV) 700

5 0 0 8

16 24 PoUT (W)

32

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TYPICAL AMPLIFIER WITH SPLIT POWER SUPPLY

LINEAR INTEGRATED CIRCUIT

+Vs
C5 100 F C3 100nF D1 1N4001

Vi

C1 1 F R3 22k

1

5 4

2
R3 680 C2 22 F C6 100 F

3

R5

C8 D2 1N4001

R4 1 RL

R1 22k

C4 C7 100nF 220nF

-Vs
BRIDGE AMPLIFIER WITH SPLIT POWER SUPPLY(POUT=34W,VS=16V, VS=-16V)
Vs+ C6 100 F C1 2.2 F 1 IN R1 22k 5 UTC TDA2030 2 3 R3 22k C4 22 F R4 680 R7 22k RL 8 4 C8 0.22 F R8 1 C7 100nF

1 R2 22k 2

5 UTC TDA2030 3 R5 22k C5 22 F R6 680 4 C9 0 22 F . R9 1

VsC2 100 F C3 100nF

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LINEAR INTEGRATED CIRCUIT

MULTIWAY SPEAKER SYSTEMS AND ACTIVE BOXES
Multiway loudspeaker systems provide the best possible acoustic performance since each loudspeaker is specially designed and optimized to handle a limited range of frequencies. Commonly, these loudspeaker systems divide the audio spectrum two or three bands. To maintain a flat frequency response over the Hi-Fi audio range the bands cobered by each loudspeaker must overlap slightly. Imbalance between the loudspeakers produces unacceptable results therefore it is important to ensure that each unit generates the correct amount of acoustic energy for its segments of the audio spectrum. In this respect it is also important to know the energy distribution of the music spectrum to determine the cutoff frequencies of the crossover filters(see Fig. 2).As an example, a 100W three-way system with crossover frequencies of 400Hz and 3KHz would require 50W for the woofer,35W for the midrange unit and 15W for the tweeter. Both active and passive filters can be used for crossovers but active filters cost significantly less than a good passive filter using aircored inductors and non-electrolytic capacitors. In addition active filters do not suffer from the typical defects of passive filters: --Power less; --Increased impedance seen by the loudspeaker(lower damping) --Difficulty of precise design due to variable loudspeaker impedance. Obviously, active crossovers can only be used if a power amplifier is provide for each drive unit. This makes it particularly interesting and economically sound to use monolithic power amplifiers. In some applications complex filters are not relay necessary and simple RC low-pass and high-pass networks(6dB/octave) can be recommended. The result obtained are excellent because this is the best type of audio filter and the only one free from phase and transient distortion. The rather poor out of band attenuation of single RC filters means that the loudspeaker must operate linearly well beyond the crossover frequency to avoid distortion. A more effective solution is shown in Fig. 3. The proposed circuit can realize combined power amplifiers and 12dB/octave or high-pass or low-pass filters. In proactive, at the input pins amplifier two equal and in-phase voltages are available, as required for the active filter operations. The impedance at the Pin(-) is of the order of 100Ω,while that of the Pin (+) is very high, which is also what was wanted.

The components values calculated for fc=900Hz using a Bessel 3rd Sallen and Key structure are: C1=C2=C3=22nF,R1=8.2KΩ,R2=5.6KΩ,R3=33KΩ. Using this type of crossover filter, a complete 3-way 60W active loudspeaker system is shown in Fig. 20. It employs 2nd order Buttherworth filter with the crossover frequencies equal to 300Hz and 3kHz. The midrange section consistors of two filters a high pass circuit followed by a low pass network. With Vs=36V the output power delivered to the woofer is 25W at d=0.06%( 30W at d=0.5%).The power delivered to the midrange and the tweeter can be optimized in the design phase taking in account the loudspeaker efficiency and impedance (RL=4Ω to 8Ω).

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LINEAR INTEGRATED CIRCUIT

It is quite common that midrange and tweeter speakers have an efficiency 3dB higher than woofers.
Vs+

Low-pass 300Hz
IN
1 F 22k 22k

2200 F

0.22 F

1.5

1N4001

1
18nF

5
UTC TDA2030

BD908

4
0.22 F 1 BD907 4 0.22 F 2200 F

680 33nF 22k 100 F

2

3
1.5

100 3.3k

1N4001

Woofer
Vs+

Band-pass 300Hz to 3KHz
0.1 F 0.1 F 22k 22k

0.22 F

1N4001

1
18nF

5
UTC TDA2030

4
1

220 F

3.3k

6.8k 3.3nF

2

3
1N4001

8 0.22 F

100 F

2.2k

Midrange
Vs+

100 0.22 F

Vs+

High-pass 3KHz
3.3 nF 3.3 nF

1N4001

1
22k

5
UTC TDA2030

4
1

100 F

22k

12k

2

3
1N4001

8 0.22 F

100 F

22k

47 F 2.2k

100

High-pass 3KHz

Tweeter

MUSICAL INSTRUMENTS AMPLIFIERS
Another important field of application for active system is music. In this area the use of several medium power amplifiers is more convenient than a single high power amplifier, and it is also more reliable. A typical example (see Fig. 4) consist of four amplifiers each driving a low-cost, 12 inch loudspeaker. This application can supply 80 to 160W rms.

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LINEAR INTEGRATED CIRCUIT

TRANSIENT INTER-MODULATION DISTORTION(TIM)
Transient inter-modulation distortion is an unfortunate phenomena associated with negative-feedback amplifiers. When a feedback amplifier receives an input signal which rises very steeply, i.e. contains high-frequency components, the feedback can arrive too late so that the amplifiers overloads and a burst of inter-modulation distortion will be produced as in Fig.5. Since transients occur frequently in music this obviously a problem for the designed of audio amplifiers. Unfortunately, heavy negative feedback is frequency used to reduce the total harmonic distortion of an amplifier, which tends to aggravate the transient inter-modulation (TIM situation.)

Fig.4 High power active box for musical instrument

Fig.5 Overshoot phenomenon in feedback amplifiers FEEDBACK PATH ¦ÂV4 INPUT PRE AMPLIFIER V1 V2 V3 POWER AMPLIFIER OUTPUT V4

20 to 40W Amplifier

20 to 40W Amplifier

V1 20 to 40W Amplifier

V2

20 to 40W Amplifier

V3 V4

The best known method for the measurement of TIM consists of feeding sine waves superimposed onto square wavers, into the amplifier under test. The output spectrum is then examined using a spectrum analyzer and compared to the input. This method suffers from serious disadvantages: the accuracy is limited, the measurement is a tatter delicate operation and an expensive spectrum analyzer is essential. The "inverting-sawtooth" method of measurement is based on the response of an amplifier to a 20KHz saw-tooth wave-form. The amplifier has no difficulty following the slow ramp but it cannot follow the fast edge. The output will follow the upper line in Fig.6 cutting of the shade area and thus increasing the mean level. If this output signal is filtered to remove the saw-tooth, direct voltage remains which indicates the amount of TIM distortion, although it is difficult to measure because it is indistinguishable from the DC offset of the amplifier. This problem is neatly avoided in the IS-TIM method by periodically inverting the saw-tooth wave-form at a low audio frequency as shown in Fig.7. In the case of the saw-tooth in Fig. 8 the mean level was increased by the TIM distortion, for a saw-tooth in the other direction the opposite is true.
SR(V/ s) m2 m1 Input Signal

Filtered Output Siganal

Fig.6 20kHz sawtooth waveform

Fig.7 Inverting sawtooth waveform 10 of 13
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UNISONIC TECHNOLOGIES CO., LTD www.unisonic.com.tw TDA2030

LINEAR INTEGRATED CIRCUIT

The result is an AC signal at the output whole peak-to-peak value is the TIM voltage, which can be measured easily with an oscilloscope. If the peak-topeak value of the signal and the peak-to-peak of the inverting sawtooth are measured, the TIM can be found very simply from:
TIM = VOUT * 100 Vsawtooth

SR(V/¦Ìs)

TIM(%)

TI M =0

TI M

=0 .1 % TI M =1 %

In Fig.8 The experimental results are shown for the 30W amplifier using the UTC TDA2030 as a driver and a low-cost complementary pair. A simple RC filter on the input of the amplifier to limit the maximum signal slope(SS) is an effective way to reduce TIM. The Diagram of Fig.9 can be used to find the Slew-Rate(SR) required for a given output power or voltage and a TIM design target. For example if an anti-TIM filter with a cutoff at 30kHz is used and the max. peak to peak output voltage is 20V then, referring to the diagram, a Slew-Rate of 6V/µs is necessary for 0.1% TIM. As shown Slew-Rates of above 10V/µs do not contribute to a further reduction in TIM. Slew-Rates of 100V/µs are not only useless but also a disadvantage in hi-fi audio amplifiers because they tend to turn the amplifier into a radio receiver.

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POWER SUPPLY

LINEAR INTEGRATED CIRCUIT

Using monolithic audio amplifier with non regulated supply correctly. In any working case it must provide a supply voltage less than the maximum value fixed by the IC breakdown voltage. It is essential to take into account all the working conditions, in particular mains fluctuations and supply voltage variations with and without load. The UTC TDA2030 (Vsmax=44V) is particularly suitable for substitution of the standard IC power amplifiers (with Vsmax=36V) for more reliable applications. An example, using a simple full-wave rectifier followed by a capacitor filter, is shown in the table and in the diagram of Fig.10. A regulated supply is not usually used for the power output stages because of its dimensioning must be done taking into account the power to supply in signal peaks. They are not only a small percentage of the total music signal, with consequently large overdimensioning of the circuit. Even if with a regulated supply higher output power can be obtained(Vs is constant in all working conditions),the additional cost and power dissipation do not usually justify its use. using non-regulated supplies, there are fewer designee restriction. In fact, when signal peaks are present, the capacitor filter acts as a flywheel supplying the required energy. In average conditions, the continuous power supplied is lower. The music power/continuous power ratio is greater in case than for the case of regulated supplied, with space saving and cost reduction.
Fig.10 DC characteristics of 50W non-regulated supply

36 34
VOUT(V)
Ripple

4 2

Ripple (Vp-p)

32 30
Vout

220V Vo 3300 F

0

28

0

0.4

0.8

1.2 IOUT(A)

1.6

2.0

Mains(220V) +20% +15% +10% — -10% -15% -20%

Secondary Voltage 28.8V 27.6V 26.4V 24V 21.6V 20.4V 19.2V

IOUT =0 43.2V 41.4V 39.6V 36.2V 32.4V 30.6V 28.8V

DC Output Voltage(VOUT) IOUT =0.1A 42V 40.3V 38.5V 35V 31.5V 29.8V 28V

IOUT =1A 37.5V 35.8V 34.2V 31V 27.8V 26V 24.3V

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SHORT CIRCUIT PROTECTION

LINEAR INTEGRATED CIRCUIT

The UTC TDA2030 has an original circuit which limits the current of the output transistors. This function can be considered as being peak power limiting rather than simple current limiting. It reduces the possibility that the device gets damaged during an accidental short circuit from AC output to Ground.

THERMAL SHUT-DOWN
The presence of a thermal limiting circuit offers the following advantages: 1).An overload on the output (even if it is permanent),or an above limit ambient temperature can be easily supported since the Tj can not be higher than 150°C 2).The heatsink can have a smaller factor of safety compared with that of a congenital circuit, There is no possibility of device damage due to high junction temperature increase up to 150°C, the thermal shut-down simply reduces the power dissipation and the current consumption.

APPLICATION SUGGESTION
The recommended values of the components are those shown on application circuit of Fig.14. Different values can be used. The following table can help the designer. SMALLER THAN LARGER THAN RECOMMENDED RECOMMENDED PURPOSE COMPONENT RECOMMENDED VALUE VALUE VALUE Closed loop gaon Increase of Gain Decrease of Gain R1 22KΩ setting. Closed loop gaon Decrease of Gain Increase of Gain R2 680Ω setting. Decrease of input Non inverting input Increase of input impedance R3 22KΩ impedance biasing Danger of oscillation at high R4 1Ω Frequency stability frequencies with inductive loads. Poor high frequencies Danger of oscillation R5 ≈3R2 Upper frequency cutoff attenuation Increase of low C1 1µF Input DC decoupling frequencies cutoff Increase of low Inverting DC C2 22µF frequencies cutoff decoupling C3,C4 0.1µF Supply voltage bypass Danger of oscillation C5,C6 100µF Supply voltage bypass Danger of oscillation C7 0.22µF Frequency stability Larger bandwidth C8 ≈1/(2π*B*R1) Upper frequency cutoff smaller bandwidth Larger bandwidth To protect the device D1,D2 1N4001 against output voltage spikes.

UTC assumes no responsibility for equipment failures that result from using products at values that exceed, even momentarily, rated values (such as maximum ratings, operating condition ranges, or other parameters) listed in products specifications of any and all UTC products described or contained herein. UTC products are not designed for use in life support appliances, devices or systems where malfunction of these products can be reasonably expected to result in personal injury. Reproduction in whole or in part is prohibited without the prior written consent of the copyright owner. The information presented in this document does not form part of any quotation or contract, is believed to be accurate and reliable and may be changed without notice.

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